Table 2. Design Parameters

9.2.2.1 Inductor Selection

Because the selection of the inductor affects the steady-state operation of a power supply, transient behavior and loop stability, the inductor is the most important component in switching power regulator design. There are three specifications most important to the performance of the inductor: inductor value, DC resistance, and saturation current. The TPS61181A device is designed to work with inductor values between 4.7 μH and 10 μH. A 4.7-μH inductor may be available in a smaller or lower profile package, while 10 μH may produce higher efficiency due to lower inductor ripple. If the boost output current is limited by the overcurrent protection of the device, using a 10-μH inductor can offer higher output current.

The internal loop compensation for the PWM control is optimized for the recommended component values, including typical tolerances. Inductor values can have ±20% tolerance with no current bias. When the inductor current approaches saturation level, its inductance can decrease 20 to 35% from the zero current value depending on how the inductor vendor defines saturation

In a boost regulator, the inductor DC current can be calculated as:

Equation 2.

where

• V_O = boost output voltage
• Io = boost output current
• V_in = boost input voltage
• η = power conversion efficiency, use 90% for TPS61181A applications

The inductor current peak-to-peak ripple can be calculated as:

Equation 3.

where

• I_pp = inductor peak-to-peak ripple
• L = inductor value
• F_s= switching frequency
• V_bat= boost input voltage

Therefore, the peak current seen by the inductor is

Equation 4.

Select the inductor with saturation current at least 25% higher than the calculated peak current. To calculate the worse case inductor peak current, use minimum input voltage, maximum output voltage and maximum load current.

Regulator efficiency is dependent on the resistance of its high current path, switching losses associated with the PWM switch and power diode. Although the TPS61181A device have optimized the internal switch resistance, the overall efficiency still relies on the DC resistance (DCR) of the inductor; lower DCR improves efficiency. However, there is a trade off between DCR and inductor footprint. Furthermore, shielded inductors typically have a higher DCR than unshielded ones. Table 3 lists recommended inductor models.

9.2.2.2 Output Capacitor Selection

During PWM brightness dimming, the load transient causes voltage ripple on the output capacitor. Since the PWM dimming frequency is in the audible frequency range, the ripple can produce audible noises on the output ceramic capacitor. There are two ways to reduce or eliminate this audible noise. The first option is to select PWM dimming frequency outside the audible range. This means the dimming frequency needs be to lower than 200 Hz or higher than 30 KHz. The potential issue with a very low dimming frequency is that WLED on/off can become visible and thus cause a flickering effect on the display. On the other hand, high dimming frequency can compromise the dimming range since the LED current accuracy and current match are difficult to maintain at low dimming duty cycle. The second option is to reduce the amount of the output ripple, and therefore minimize the audible noise.

The TPS61181A adopts a patented technology to limit output ripple even with small output capacitance. In a typical application, the output ripple is less than 200 mV during PWM dimming with a 4.7-μF output capacitor, and the audible noise is not noticeable. The devices are designed to be stable with output capacitor down to 1 μF. However, the output ripple will increase with lower output capacitor.

Care must be taken when evaluating the derating of a ceramic capacitor due to applied dc voltage, aging and over frequency. For example, larger form factor capacitors (in 1206 size) have their self resonant frequencies in the switching frequency range of the TPS61181A. So the effective capacitance is significantly lower. Therefore, it may be necessary to use small capacitors in parallel instead of one large capacitor.

9.2.2.3 Audible Noise Reduction

Ceramic capacitors can produce audible noise if the frequency of its AC voltage ripple is in the audible frequency range. In TPS61181A applications, both input and output capacitors are subject to AC voltage ripple during PWM brightness dimming. The device integrates a patented technology to minimize the ripple voltage, and thus audible noises.

To further reduce the audible noise, one effective way is to use two or three small size capacitors in parallel instead of one large capacitor. The application circuit in Figure 16 uses two 2.2-μF/25-V ceramic capacitors at the input and two 1-μF/50-V ceramic capacitors at the output. All of the capacitors are in 0805 package. Although the output ripple during PWM dimming is higher than with one 4.7 μF in a 1206 package, the overall audible noise is lower.

In addition, connecting a 10-nF/50V ceramic capacitor between the V_O pin and IFB1 pin can further reduce the output AC ripple during the PWM dimming. Since this capacitor is subject to large AC ripple, choose a small package such as 0402 to prevent it from producing noise.

9.2.2.4 Isolation MOSFET Selection

The TPS61181A provides a gate driver to an external P-channel MOSFET which can be turned off during device shutdown or fault condition. This MOSFET can provide a true shutdown function, and also protect the battery from output short circuit conditions. The source of the PMOS must be connected to the input, and a pullup resistor is required between the source and gate of the FET to keep the FET off during device shutdown. To turn on the isolation FET, the Fault pin is pulled low, and clamped at 8 V below the V_BAT pin voltage.

During device shutdown or fault condition, the isolation FET is turned off, and the input voltage is applied on the isolation MOSFET. During a short circuit condition, the catch diode (D2 in typical application circuit) is forward biased when the isolation FET is turned off. The drain of the isolation FET swings below ground. The voltage across the isolation FET can be momentarily greater than the input voltage. Therefore, select a 30-V MOSFET for a 24-V maximum input. The on resistance of the FET has a large impact on power conversion efficiency since the FET carries the input voltage. Select a MOSFET with R_ds(on) less than 100 mΩ to limit the power losses.