8.1.1 ADC Input Driver

The input driver circuit for a high-precision ADC mainly consists of two parts: a driving amplifier and a fly-wheel RC filter. The amplifier is used for signal conditioning of the input signal and its low output impedance provides a buffer between the signal source and the switched capacitor inputs of the ADC. The RC filter helps attenuate the sampling charge injection from the switched-capacitor input stage of the ADC and functions as an antialiasing filter to band-limit the wideband noise contributed by the front-end circuit. Careful design of the front-end circuit is critical to meet the linearity and noise performance of the ADS9110.

8.1.2 Input Amplifier Selection

Selection criteria for the input amplifiers is highly dependent on the input signal type as well as the performance goals of the data acquisition system. Some key amplifier specifications to consider when selecting an appropriate amplifier to drive the inputs of the ADC are:

• Small-signal bandwidth. Select the small-signal bandwidth of the input amplifiers to be as high as possible after meeting the power budget of the system. Higher bandwidth reduces the closed-loop output impedance of the amplifier, thus allowing the amplifier to more easily drive the low cutoff frequency RC filter (see the Antialiasing Filter section) at the inputs of the ADC. Higher bandwidth also minimizes the harmonic distortion at higher input frequencies. In order to maintain the overall stability of the input driver circuit, select the amplifier with Unity Gain Bandwidth (UGB) as described in Equation 14:
Equation 14.
• Noise. Noise contribution of the front-end amplifiers must be as low as possible to prevent any degradation in SNR performance of the system. Generally, to ensure that the noise performance of the data acquisition system is not limited by the front-end circuit, the total noise contribution from the front-end circuit must be kept below 20% of the input-referred noise of the ADC. Noise from the input driver circuit is band-limited by designing a low cutoff frequency RC filter, as explained in Equation 15.
Equation 15.
where
• V_{1 / f_AMP_PP} is the peak-to-peak flicker noise in µV,
• e_{n_RMS} is the amplifier broadband noise density in nV/√Hz,
• f_–3dB is the 3-dB bandwidth of the RC filter, and
• N_G is the noise gain of the front-end circuit that is equal to 1 in a buffer configuration.
• Distortion. Both the ADC and the input driver introduce distortion in a data acquisition block. To ensure that the distortion performance of the data acquisition system is not limited by the front-end circuit, the distortion of the input driver must be at least 10 dB lower than the distortion of the ADC, as shown in Equation 16.
Equation 16.
• Settling Time. For dc signals with fast transients that are common in a multiplexed application, the input signal must settle within an 18-bit accuracy at the device inputs during the acquisition time window. This condition is critical to maintain the overall linearity performance of the ADC. Typically, the amplifier data sheets specify the output settling performance only up to 0.1% to 0.001%, which may not be sufficient for the desired 18-bit accuracy. Therefore, always verify the settling behavior of the input driver by TINA™-SPICE simulations before selecting the amplifier.

8.1.3 Antialiasing Filter

Converting analog-to-digital signals requires sampling an input signal at a constant rate. Any higher-frequency content in the input signal beyond half the sampling frequency is digitized and folded back into the low-frequency spectrum. This process is called aliasing. Therefore, an analog, antialiasing filter must be used to remove the harmonic content from the input signal before being sampled by the ADC. An antialiasing filter is designed as a low-pass, RC filter, where the 3-dB bandwidth is optimized based on specific application requirements. For dc signals with fast transients (including multiplexed input signals), a high-bandwidth filter is designed to allow accurately settling the signal at the inputs of the ADC during the small acquisition time window. For ac signals, keep the filter bandwidth low to band-limit the noise fed into the input of the ADC, thereby increasing the signal-to-noise ratio (SNR) of the system.

Besides filtering the noise from the front-end drive circuitry, the RC filter also helps attenuate the sampling charge injection from the switched-capacitor input stage of the ADC. A filter capacitor, C_FLT, is connected from each input pin of the ADC to the ground (as shown in Figure 93). This capacitor helps reduce the sampling charge injection and provides a charge bucket to quickly charge the internal sample-and-hold capacitors during the acquisition process. Generally, the value of this capacitor must be at least 15 times the specified value of the ADC sampling capacitance. For the ADS9110, the input sampling capacitance is equal to 60 pF, thus it is recommeded to keep C_FLT greater than 900 pF. The capacitor must be a COG- or NPO-type because these capacitor types have a high-Q, low-temperature coefficient, and stable electrical characteristics under varying voltages, frequency, and time.

Figure 93. Antialiasing Filter Configuration

Note that driving capacitive loads can degrade the phase margin of the input amplifiers, thus making the amplifier marginally unstable. To avoid amplifier stability issues, series isolation resistors (R_FLT) are used at the output of the amplifiers. A higher value of R_FLT is helpful from the amplifier stability perspective, but adds distortion as a result of interactions with the nonlinear input impedance of the ADC. Distortion increases with source impedance, input signal frequency, and input signal amplitude. Therefore, the selection of R_FLT requires balancing the stability and distortion of the design. For the ADS9110, limiting the value of R_FLT to a maximum of 10-Ω is recommended in order to avoid any significant degradation in linearity performance. The tolerance of the selected resistors must be kept less than 1% to keep the inputs balanced.

The driver amplifier must be selected such that its closed-loop output impedance is at least 5X lesser than the R_FLT.

8.1.4 ADC Reference Driver

The external reference source to the ADS9110 must provide low-drift and very accurate voltage for the ADC reference input and support the dynamic charge requirements without affecting the noise and linearity performance of the device. The output broadband noise of most references can be in the order of a few hundred μV_RMS. Therefore, to prevent any degradation in the noise performance of the ADC, the output of the voltage reference must be appropriately filtered by using a low-pass filter with a cutoff frequency of a few hundred hertz.

After band-limiting the noise of the reference circuit, the next important step is to design a reference buffer that can drive the dynamic load posed by the reference input of the ADC. The reference buffer must regulate the voltage at the reference pin such that the value of V_REF stays within the 1-LSB error at the start of each conversion. This condition necessitates the use of a large capacitor, CBUF_FLT (see Figure 39), between each pair of REFP and REFM pins for regulating the voltage at the reference input of the ADC. The effective capacitance of any large capacitor reduces with the applied voltage based on the voltage rating and type. Using X7R-type capacitors is strongly recommended.

The amplifier selected as the reference driver must have an extremely low offset and temperature drift with a low output impedance to drive the capacitor at the ADC reference pins without any stability issues.

8.2.1 Design Requirements

Design an application circuit optimized for using the ADS9110 to achieve:

• > 98.5-dB SNR, < –118-dB THD,
• ±1-LSB linearity, and
• Maximum-specified throughput of 2 MSPS

8.2.2 Detailed Design Procedure

The application circuits are illustrated in Figure 94. For simplicity, power-supply decoupling capacitors are not shown in these circuit diagrams; see the Power-Supply Recommendations section for suggested guidelines.

The input signal is processed through the OPA625 (a high-bandwidth, low-distortion, high-precision amplifier in an inverting gain configuration) and a low-pass RC filter before being fed into the ADC. Generally, the distortion from the input driver must be at least 10 dB less than the ADC distortion. The distortion resulting from variation in the common-mode signal is eliminated by using the OPA625 in an inverting gain configuration. The low-power OPA625 as an input driver provides exceptional ac performance because of its extremely low-distortion and high-bandwidth specifications. To exercise the complete dynamic range of the ADS9110, the common-mode voltage at the ADS9110 inputs is established at a value of 2.25 V (4.5 V / 2) by using the noninverting pins of the OPA625 amplifiers.

In addition, the components of the antialiasing filter are such that the noise from the front-end circuit is kept low without adding distortion to the input signal.

The reference driver circuit, illustrated in Figure 94, generates a voltage of 4.5 V_DC using a single 5-V supply. This circuit is suitable to drive the reference of the ADS9110 at higher sampling rates up to 2 MSPS. The reference voltage of 4.5 V in this design is generated by the high-precision, low-noise REF5045 circuit. The output broadband noise of the reference is heavily filtered by a low-pass filter with a 3-dB cutoff frequency of 160 Hz.

The reference buffer is designed with the OPA625 and OPA378 in a composite architecture to achieve superior dc and ac performance at a reduced power consumption, compared to using a single high-performance amplifier. The OPA625 is a high-bandwidth amplifier with a very low open-loop output impedance of 1 Ω up to a frequency of 1 MHz. The low open-loop output impedance makes the OPA625 a good choice for driving a high capacitive load to regulate the voltage at the reference input of the ADC. The relatively higher offset and drift specifications of the OPA625 are corrected by using a dc-correcting amplifier (the OPA378) inside the feedback loop. The composite scheme inherits the extremely low offset and temperature drift specifications of the OPA378.

8.2.3 Application Curves

fIN = 2 kHz, SNR = 99 dB, THD = –120 dB

Figure 95. FFT with a 2-kHz Input Signal

Typical INL of ±0.5 LSB

Figure 96. Typical INL